EECT 7327 Fall 2014 Oversampling ADC Nyquist Rate ADC 2 Data Converters Oversampling ADC Professor Y Chiu EECT 7327 Fall 2014 The black box version of the quantization process ID: 674339
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Slide1
– 1 –
Data Converters Oversampling ADC Professor Y. ChiuEECT 7327 Fall 2014
Oversampling ADCSlide2
Nyquist-Rate ADC
– 2 –
Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
The “black box” version of the quantization process
Digitizes the input signal up to the Nyquist frequency (fs/2)Minimum sampling frequency (fs) for a given input bandwidthEach sample is digitized to the maximum resolution of the converterSlide3
Anti-Aliasing Filter (AAF)
– 3 –Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
Input signal must be band-limited prior to sampling
Nyquist sampling places stringent requirement on the roll-off characteristic of AAF
Often some oversampling is employed to relax the AAF design (better phase response too)Decimation filter (digital) can be linear-phaseSlide4
Oversampling ADC–
4 –Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
Sample rate is well beyond the signal bandwidth
Coarse quantization is combined with feedback to provide an accurate estimate of the input signal on an “average” sense
Quantization error in the coarse digital output can be removed by the digital decimation filterThe resolution/accuracy of oversampling converters is achieved in a sequence of samples (“average” sense) rather than a single sample; the usual concept of DNL and INL of Nyquist converters are not applicableSlide5
Relaxed AAF Requirement–
5 –Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
Nyquist-rate converters
Oversampling converters
Sub-sampling
Band-pass oversampling
OSR =
f
s
/2
f
mSlide6
Oversampling ADC–
6 –Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
Predictive type
Delta modulation
Noise-shaping typeSigma-delta modulationMulti-level (quantization) sigma-delta modulationMulti-stage (cascaded) sigma-delta modulation (MASH)Slide7
Oversampling–
7 –Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
Nyquist
Oversampled
Sample rate
Noise power
Power
Nyquist
f
s
Δ
2
/12
P
Oversampled
M*
f
s
(
Δ
2
/12)/M
M*P
OSR = MSlide8
Noise Shaping–
8 –Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
Push noise out of signal band
Large gain @ LF, low gain @ HF
→ Integrator?
Slide9
Sigma-Delta (ΣΔ) Modulator
– 9 –
Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
Noise shaping obtained with an integrator
Output subtracted from input to avoid integrator saturation
First-order
ΣΔ
modulatorSlide10
Linearized Discrete-Time Model
– 10 –Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
Caveat: E(z) may be correlated with X(z) – not “white”!Slide11
First-Order Noise Shaping
– 11 –Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
Doubling OSR (M) increases SQNR by 9 dB (1.5 bit/oct)Slide12
SC Implementation–
12 –Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
SC integrator
1-bit ADC
→ simple, ZX detector1-bit feedback DAC → simple, inherently linearSlide13
Second-Order ΣΔ Modulator
– 13 –
Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
Doubling OSR (M) increases SQNR by 15 dB (2.5 bit/oct)Slide14
2nd-Order ΣΔ Modulator (1-Bit
Quantizer)–
14
–
Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014Simple, stable, highly-linearInsensitive to component mismatchLess correlation b/t E(z) and X(z)Slide15
Generalization (Lth-Order Noise Shaping)
– 15 –
Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
Doubling OSR (M) increases SQNR by (6L+3) dB, or (L+0.5) bit
Potential instability for
3rd- and higher-order single-loop
ΣΔ
modulatorsSlide16
ΣΔ vs. Nyquist
ADC’s– 16
–
Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
ΣΔ ADC output (1-bit)Nyquist ADC output
ΣΔ
ADC behaves quite differently from Nyquist converters
Digital codes only display an “average” impression of the input
INL, DNL, monotonicity, missing code, etc. do not directly apply in
ΣΔ
converters
→ use SNR, SNDR, SFDR insteadSlide17
Tones–
17 –Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
The output spectrum corresponding to V
i
= 0 results in a tone at
f
s
/2, and will get eliminated by the decimation filter
The 2nd output not only has a tone at
f
s
/2, but also a low-frequency tone –
f
s
/2000 – that cannot be eliminated by the decimation filterSlide18
Tones–
18 –Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
Origin – the quantization error spectrum of the low-resolution ADC (1-bit in the previous example) in a
ΣΔ
modulator is NOT white, but correlated with the input signal, especially for idle (DC) inputs. (R. Gray, “Spectral analysis of sigma-delta quantization noise”)Approaches to “whitening” the error spectrumDither – high-frequency noise added in the loop to randomize the quantization error. Drawback is that large dither consumes the input dynamic range.
Multi-level quantization. Needs linear multi-level DAC.
High-order single-loop
ΣΔ
modulator. Potentially unstable.
Cascaded (MASH)
ΣΔ
modulator. Sensitive to mismatch.Slide19
Cascaded (MASH) ΣΔ Modulator
– 19 –
Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
Idea: to further quantize E(z) and later subtract out in digital domain
The 2nd quantizer can be a
ΣΔ
modulator as wellSlide20
2-1 Cascaded Modulator
– 20 –
Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
DNTFSlide21
2-1 Cascaded Modulator
– 21 –
Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
E
1
(z) completely cancelled assuming perfect matching between the modulator NTF (analog domain) and the DNTF (digital domain)
A 3rd-order noise shaping on E
2
(z) obtained
No potential instability problemSlide22
Integrator Noise–
22 –Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
Delay ignored
INT1 dominates
the overall noise
Performance!Slide23
References–
23 –Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
B. E.
Boser
and B. A. Wooley, JSSC, pp. 1298-1308, issue 6, 1988.B. H. Leung et al., JSSC, pp. 1351-1357, issue 6, 1988.T. C. Leslie and B. Singh, ISCAS, 1990, pp. 372-375.B. P. Brandt and B. A. Wooley
, JSSC, pp. 1746-1756, issue 12, 1991.
F. Chen and B. H. Leung, JSSC, pp. 453-460, issue 4, 1995.
R. T. Baird and T. S.
Fiez
, TCAS2, pp. 753-762, issue 12, 1995.
T. L. Brooks et al., JSSC, pp. 1896-1906, issue 12, 1997.
A. K.
Ong
and B. A.
Wooley
, JSSC, pp. 1920-1934, issue 12, 1997.
S. A.
Jantzi
,
K. W. Martin, and A.S.
Sedra
, JSSC, pp. 1935-1950, issue 12, 1997.
A. Yasuda,
H.
Tanimoto
, and T. Iida,
JSSC, pp. 1879-1886, issue 12, 1998.A. R. Feldman, B. E. Boser
, and P. R. Gray, JSSC, pp. 1462-1469, issue 10, 1998.H. Tao and J. M. Khoury, JSSC, pp. 1741-1752, issue 12, 1999.
E. J. van der Zwan et al., JSSC, pp. 1810-1819, issue 12, 2000.I. Fujimori et al., JSSC, pp. 1820-1828, issue 12, 2000.
Y. Geerts, M.S.J. Steyaert, W. Sansen,
JSSC, pp. 1829-1840, issue 12, 2000.Slide24
References–
24 –Data Converters Oversampling ADC Professor Y. Chiu
EECT 7327
Fall 2014
T. Burger and Q. Huang, JSSC, pp. 1868-1878, issue 12, 2001.
K.
Vleugels, S. Rabii, and B. A. Wooley, JSSC, pp. 1887-1899, issue 12, 2001.S. K. Gupta and
V.
Fong,
JSSC, pp. 1653-1661, issue 12, 2002.
R.
Schreier
et al., JSSC, pp. 1636-1644, issue 12, 2002.
J. Silva et al., CICC, 2002, pp. 183-190.
Y.-I. Park et al., CICC, 2003, pp. 115-118.
L. J.
Breems
et al., JSSC, pp. 2152-2160, issue 12, 2004.
R. Jiang and T. S.
Fiez
, JSSC, pp. 63-74, issue 12, 2004.
P.
Balmelli
and Q. Huang, JSSC, pp. 2161-2169, issue 12, 2004.
K. Y. Nam et al., CICC, 2004, pp. 515-518.
X. Wang et al., CICC, 2004, pp. 523-526.
A.
Bosi et al., ISSCC, 2005, pp. 174-175.N.
Yaghini and D. Johns, ISSCC, 2005, pp. 502-503.G. Mitteregger et al., JSSC, pp. 2641-2649, issue 12, 2006.R.
Schreier et al., JSSC, pp. 2632-2640, issue 12, 2006.